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device operating temperature range package semiconductor technical data wideband fm if subsystem for dect and digital applications ordering information MC13158FTB t a = 40 to +85 c tqfp32 ftb suffix plastic package case 873 (thin qfp) 32 1 order this document by mc13158/d 1 motorola analog ic device data
the mc13158 is a wideband if subsystem that is designed for high performance data and analog applications. excellent high frequency performance is achieved, with low cost, through the use of motorola's mosaic 1.5 ? rf bipolar process. the mc13158 has an onboard grounded collector vco transistor that may be used with a fundamental or overtone crystal in single channel operation or with a pll in multichannel operation. the mixer is useful to 500 mhz and may be used in a balanced differential or single ended configuration. the if amplifier is split to accommodate two low cost cascaded filters. rssi output is derived by summing the output of both if sections. a precision data shaper has an off function to shut the output off to save current. an enable control is provided to power down the ic for power management in battery operated applications. applications include dect, wideband wireless data links for personal and portable laptop computers and other battery operated radio systems which utilize gfsk, fsk or fm modulation. ? designed for dect applications ? 1.8 to 6.0 vdc operating voltage ? low power consumption in active and standby mode ? greater than 600 khz detector bandwidth ? data slicer with special off function ? enable function for power down of battery operated systems ? rssi dynamic range of 80 db minimum ? low external component count representative block diagram this device contains 234 active transistors. rssi 25 32 31 30 29 28 27 26 24 23 22 21 20 19 18 17 enable v ee1 n/c osc base osc emit n/c mix in1 mix in2 rssi buf ds gnd ds out ds in2 ds aoffo ds in1 det out if amp lim amp 5.0 p bias data slicer mc13158 16 v ee2 15 det gain 14 n/c 13 quad 12 lim out 11 n/c 10 lim dec2 9 lim dec1 1 2 3 4 5 6 7 8 mix out v cc1 if in if dec1 if dec2 if out v cc2 lim in ? motorola, inc. 1996 rev 1
mc13158 2 motorola analog ic device data maximum ratings rating pin symbol value unit power supply voltage 16, 26 v s(max) 6.5 vdc junction temperature t jmax +150 c storage temperature range t stg 65 to +150 c note: 1. devices should not be operated at or outside these values. the arecommended operating conditionso provide for actual device operation. recommended operating conditions (v cc = v 2 = v 7 ; v ee = v 16 = v 22 = v 26 ; v s = v cc v ee ) rating pin symbol value unit power supply voltage 2, 7 v s 2.0 to 6.0 vdc t a = 25 c 40 c t a 85 c 16, 26 input frequency 31, 32 f in 10 to 500 mhz ambient temperature range t a 40 to + 85 c input signal level 31, 32 v in 200 mvrms dc electrical characteristics (t a = 25 c; v s = 3.0 vdc; no input signal; see figure 1.) characteristic condition pin symbol min typ max unit total drain current v s = 2.0 vdc 16, 26 i total 2.5 5.5 8.5 ma v s = 3.0 vdc 3.5 5.7 8.5 v s = 6.0 vdc 3.5 6.0 9.5 see figure 2 data slicer (input voltage referenced to v ee ; v s = 3.0 vdc; no input signal) output current; v 18 lo; v 19 = v ee 21 i 21 2.0 5.9 ma data slicer enabled (ds aono) v 18 < v 20 v 20 = v s /2 see figure 3 output current; v 18 hi; v 19 = v ee 21 i 21 0.1 1.0 m a data slicer enabled (ds aono) v 18 > v 20 v 20 = v s /2 see figure 4 output current; v 19 = v cc 21 i 21 0.1 1.0 m a data slicer disabled (ds aoffo) v 20 = v s /2 ac electrical characteristics (t a = 25 c; v s = 3.0 vdc; f rf = 110.7 mhz; f lo = 100 mhz; see figure 1.) characteristic condition pin symbol min typ max unit mixer mixer conversion gain v in = 1.0 mvrms 31, 32, 1 22 db see figure 5 noise figure input matched 31, 32, 1 nf 14 db mixer input impedance singleended 31, 32 rp 865 w see figure 15 cp 1.6 pf mixer output impedance 1 330 w
mc13158 3 motorola analog ic device data ac electrical characteristics (continued) (t a = 25 c; v s = 3.0 vdc; f rf = 110.7 mhz; f lo = 100 mhz; see figure 1.) characteristic condition pin symbol min typ max unit if amplifier section if rssi slope see figure 8 23 0.15 0.3 0.4 m a/db if gain f = 10.7 mhz 3, 6 36 db see figure 7 input impedance 3 330 w output impedance 6 330 w limiting amplifier section limiter rssi slope see figure 9 23 0.15 0.3 0.4 m a/db limiter gain f = 10.7 mhz 8, 12 70 db input impedance 8 330 w lim dec1 lim in a v a 100 n figure 1. test circuit rssi 25 32 31 30 29 28 27 26 24 23 21 20 19 18 17 enable v ee1 n/c osc base osc emit n/c mix in1 mix in2 rssi buf ds gnd ds out ds in2 ds aoffo ds in1 det out lim amp 5.0 p bias data slicer mc13158 16 v ee2 15 det gain 14 n/c quad 12 lim out 11 n/c 10 lim dec2 9 2 3 4 5 6 7 8 mix out v cc1 if in if dec1 if dec2 if out v cc2 1 1.0 n 100 n 1.0 n 1.0 n 100 n 100 n 100 n 50 330 50 330 mixer output if input if output limiter input 6.8 k 200 pf 1.0 n 1.0 n 1.0 m h 3.0 vdc 13 100 k 51 k 0 to 3.0 vdc 3.0 vdc 1.5 vdc 100 m a 2.3 vdc a 3.0 vdc 50 rf input 110.7 mhz 1:4 lo input 100 mhz 200 mvrms 200 a 3.0 vdc 0 to 3.0 vdc 22
mc13158 4 motorola analog ic device data typical performance over temperature (per figure 1) figure 2. total supply current versus ambient temperature, supply voltage 40 0.6 40 0.2 20 8.5 40 7.0 40 0.12 20 6.4 normalized if amp gain (db) t a , ambient temperature ( c) normalized mixer gain (db) t a , ambient temperature ( c) data slicer output current (ma) t a , ambient temperature ( c) mixer rssi output current ( a) m t a , ambient temperature ( c) data slicer output current ( a) m t a , ambient temperature ( c) i total , total supply current (ma) t a , ambient temperature ( c) figure 3. data slicer on output current versus ambient temperature figure 4. data slicer on output current versus ambient temperature figure 5. normalized mixer gain versus ambient temperature figure 6. mixer rssi output current versus ambient temperature, mixer input level figure 7. normalized if amp gain versus ambient temperature 0 20 40 60 80 100 120 0 20 40 60 80 100 120 20 0 20 40 60 80 100 120 20 0 20 40 60 80 100 120 20 0 20 40 60 80 20 0 20 40 60 80 100 120 100 120 6.2 6.0 5.8 5.6 5.4 5.2 4.8 8.0 7.5 7.0 6.5 6.0 5.5 5.0 0.10 0.08 0.06 0.04 0.02 0.1 0 0.1 0.2 0.3 0.4 0.5 0.6 0.4 0.2 0 0.2 0.4 0.6 0.8 6.0 5.0 4.0 3.0 2.0 5.0 3.0 v 2.0 v data slicer aono v 19 = v cc v 20 = v s /2 v in = 1.0 mvrms v s = 3.0 vdc f c = 110.7 mhz f lo = 100 mhz v s = 3.0 vdc f c = 110.7 mhz f lo = 100 mhz v 18 > v 20 v s = 3.0 vdc f = 10.7 mhz v in = 1.0 mvrms v s = 6.0 v data slicer aono v 19 = v ee v 20 = v s /2 v 18 < v 20 v in = 1.0 mvrms v in = 10 mvrms
mc13158 5 motorola analog ic device data ttypical performance over temperature (per figure 1) figure 8. if amp rssi output current versus ambient temperature, if input level 40 1.20 demodulator output dc voltage (vdc) t a , ambient temperature ( c) 1.15 1.10 1.05 1.00 0.95 0.90 20 0 20 40 60 80 100 120 40 8.0 40 0.60 40 10 limiter amp rssi output current ( a) m t a , ambient temperature ( c) total rssi output current ( a) m t a , ambient temperature ( c) if amp rssi output current ( a) m t a , ambient temperature ( c) 9.0 7.0 6.0 5.0 4.0 3.0 6.0 4.0 2.0 0 2.0 0.55 0.50 0.45 0.40 0.35 20 0 20 40 60 80 20 0 20 40 60 80 100 120 100 120 20 0 20 40 60 80 100 120 2.0 8.0 v s = 3.0 vdc f = 10.7 mhz v s = 3.0 vdc f = 10.7 mhz v in = 100 mvrms v in = 10 mvrms v in = 1.0 mvrms v in = 100 m vrms v s = 3.0 vdc r 17 = 51 k r 15 = 100 k v s = 3.0 vdc no input signal figure 9. limiter amp rssi output current versus ambient temperature, input signal level figure 10. total rssi output current versus ambient temperature (no signal) figure 11. demodulator dc voltage versus ambient temperature v in = 10 mvrms v in = 1.0 mvrms system level ac electrical characteristics (t a = 25 c; v s = 3.0 vdc; f rf = 112 mhz; f lo = 122.7 mhz) characteristic condition notes symbol typ unit 12 db sinad sensitivity: f rf = 112 mhz 1 dbm narrowband application f mod = 1.0 khz f dev = 125 khz sinad curve without preamp figure 25 101 with preamp figure 26 113 third order intercept point f rf1 = 112 mhz 2 iip3 32 dbm f rf2 = 112.1 mhz 1.0 db comp. point v s = 3.5 vdc 1.0 db c.pt. 39 figure 28 notes: 1. test circuit & test set per figure 24. 2. test circuit & test set per figure 27.
mc13158 6 motorola analog ic device data circuit description general the mc13158 is a low power single conversion wideband fm receiver incorporating a split if. this device is designated for use as the backend in digital fm systems such as digital european cordless telephone (dect) and wideband data links with data rates up to 2.0 mbps. it contains a mixer, oscillator, received signal strength indicator (rssi), if amplifier, limiting if, quadrature detector, power down or enable function, and a data slicer with output off function. further details are covered in the pin function description which shows the equivalent internal circuit and external circuit requirements. current regulation/enable temperature compensating voltage independent current regulators which are controlled by the enable pin (pin 25) where alowo powers up and ahigho powers down the entire circuit. mixer the mixer is a doublebalanced four quadrant multiplier and is designed to work up to 500 mhz. it can be used in differential or in single ended mode by connecting the other input to the positive supply rail. the linear gain of the mixer is approximately 22 db at 100 mvrms lo drive level. the mixer gain and noise figure have been emphasized at the expense of intermodulation performance. rssi measurements are added in the mixer to extend the range to higher signal levels. the singleended parallel equivalent input impedance of the mixer is rp ~ 1.0 k w and cp ~ 2.0 pf. the buffered output of the mixer is internally loaded resulting in an output impedance of 330 w . local oscillator the onchip transistor operates with crystal and lc resonant elements up to 220 mhz. series resonant, overtone crystals are used to achieve excellent local oscillator stability. third overtone crystals are used through about 65 to 70 mhz. operation from 70 mhz up to 180 mhz is feasible using the onchip transistor with a 5th or 7th overtone crystal. to enhance operation using an overtone crystal, the internal transistor bias is increased by adding an external resistor from pin 29 to v ee ; however, with an external resistor the oscillator stays on during power down. typically, 10 dbm of local oscillator drive is needed to adequately drive the mixer. with an external oscillator source, the ic can be operated up to 500 mhz. rssi the received signal strength indicator (rssi) output is a current proportional to the log of the received signal amplitude. the rssi current output is derived by summing the currents from the mixer, if and limiting amplifier stages. an increase in rssi dynamic range, particularly at higher input signal levels is achieved. the rssi circuit is designed to provide typically 85 db of dynamic range with temperature compensation. linearity of the rssi is optimized by using external ceramic bandpass filters which have an insertion loss of 4.0 db and 330 w source and load impedance. for higher data rates used in dect and related applications, lc bandpass filtering is necessary to acquire the desired bandpass response; however, the rssi linearity will require the same insertion loss. rssi buffer the rssi output current creates a voltage across an external resistor. a unity voltagegain amplifier is used to buffer this voltage. the output of this buffer has an active pullup but no pulldown, so it can also be used as a peak detector. the negative slew rate is determined by external capacitance and resistance to the negative supply. if amplifier the first if amplifier section is composed of three differential stages with the second and third stages contributing to the rssi. this section has internal dc feedback and external input decoupling for improved symmetry and stability. the total gain of the if amplifier block is approximately 40 db at 10.7 mhz. the fixed internal input impedance is 330 w . when using ceramic filters requiring source and loss impedances of 330 w , no external matching is necessary. overall rssi linearity is dependent on having total midband attenuation of 10 db (4.0 db insertion loss plus 6.0 db impedance matching loss) for the filter. the output of the if amplifier is buffered and the impedance is 330 w . limiter the limiter section is similar to the if amplifier section except that five differential stages are used. the fixed internal input impedance is 330 w . the total gain of the limiting amplifier section is approximately 70 db. this if limiting amplifier section internally drives the quadrature detector section and it is also brought out on pin 12. quadrature detector the quadrature detector is a doubly balanced four quadrant multiplier with an internal 5.0 pf quadrature capacitor between pins 12 and 13. an external capacitor may be added between these pins to increase the if signal to the external parallel rlc resonant circuit that provides the 90 degree phase shift and drives the quadrature detector. a single pin (pin 13) provides for the external lc parallel resonant network and the internal connection to the quadrature detector. internal low pass filter capacitors have been selected to control the bandwidth of the detector. the recovered signal is brought out by the inverting amplifier buffer. an external feedback resistor from the output (pin 17) to the input of the inverting amplifier (pin 15) controls the output amplitude; it is combined with another external resistor from the input to the negative supply (pin 16) to set the output dc level. for a resistor ratio of 1, the dc level at the detector output is 2.0 v be (see figure 12). a small capacitor c 17 across the first resistor (from pin 17 to 15) can be used to reduce the bandwidth. data slicer the data slicer is a comparator that is designed to square up the data signal. across the data slicer inputs (pins 18 and 20) are back to back diodes.
mc13158 7 motorola analog ic device data the recovered data signal from the quadrature detector can be dc coupled to the data slicer ds in1 (pin 18). in the application circuit shown in figure 1 it will be centered at 2.0 v be and allowed to swing v be . a capacitor is placed from ds in2 (pin 20) to v ee . the size of this capacitor and the nature of the data signal determine how faithfully the data slicer shapes up the recovered signal. the time constant is short for large peak to peak voltage swings or when there is a change in dc level at the detector output. for small signal or for continuous bits of the same polarity which drift close to the threshold voltage, the time constant is longer. a unique feature of the data slicer is that the inverting switching stages in the comparator are supplied through the emitter pin of the output transistor (pin 22 ds gnd) to v ee rather than internally to v ee . this is provided in order to reduce switching feedback to the front end. a control pin is provided to shut the data slicer output off (ds aoffo pin 19). with ds aoffo pin at v cc the data slicer output is shut off by shutting down the base drive to the output transistor. when a channel is being monitored to make an rssi measurement, but not to collect data, the data output may be shut off to save current. pin function description pin symbol internal equivalent circuit description/external circuit requirements 1 2 mix out v cc1 mix out 1 v cc1 2 mixer output the mixer output impedance is 330 w ; it matches to 10.7 mhz ceramic filters with 330 w input impedance. supply voltage (v cc1 ) this pin is the v cc pin for the mixer, local oscillator, and if amplifer. the operating out v ee1 26 oscillator , and if amplifer . the operating supply voltage range is from 1.8 vdc to 5.0 vdc. in the pcb layout, the v cc trace must be kept as wide as possible to minimize inductive reactances along the trace; it is best to have it completely fill around the surface mount components and traces on the circuit side of the pcb. 3 4 if in if 330 64 k 64 k if dec2 5 v cc1 2 if input the input impedance at pin 3 is 330 w . it matches the 330 w load impedance of a 10.7 mhz ceramic filter. thus, no external matching is required. if dec1 & dec2 5 dec1 if dec2 if dec1 4 if in 3 v ee1 26 if decoupling pins. decoupling capacitors should be placed directly at the pins to enhance stability. two capacitors are decoupled to the rf ground v cc1 ; one is placed between dec1 & dec2. 6 if out if out 5 v ee1 26 v cc1 2 if output the output impedance is 330 w ; it matches the 330 input resistance of a 10.7 mhz ceramic filter.
mc13158 8 motorola analog ic device data pin function description (continued) description/external circuit requirements internal equivalent circuit symbol pin 7 v cc2 330 64 k 64 k li 10 v cc2 7 supply voltage (v cc2 ) this pin is v cc supply for the limiter, quadrature detector, data slicer and rssi buffer circuits. in the application pc board this pin is tied to a common v cc trace with v cc1 . 8 9 lim in lim dec1 330 64 k lim dec2 limiter input the limiter input impedance is 330 w . limiter decou p lin g 10 dec1 lim dec2 lim dec1 9 lim in 8 v ee2 16 limiter decoupling decoupling capacitors are placed directly at these pins and to v cc (rf ground). use the same procedure as in the if decoupling. 11,14, 27 & 28 n/c no connects there is no internal connection to these pins; however it is recommended that these pins be connected externally to v cc (rf ground). 12 lim out 13 quad 12 lim out v cc2 7 limiter output the output impedance is low. the limiter drives a quadrature detector circuit with in phase and quadrature phase signals. 13 quad 16 v ee2 5.0 p quadrature detector circuit the quadrature detector is a doubly balanced fourquadrant multiplier with an internal 5.0 pf capacitor between pins 12 and 13. an external capacitor may be added to increase the if signal to pin 13. the quadrature detector pin is provided to connect the external rlc parallel resonant network which provides the 90 degree phase shift and drives the quadrature detector. 15 17 det gain det out det out 17 det 15 7 v cc2 detector buffer amplifier this is an inverting amplifier. an external feed- back resistor from pin 17 to 15, (the inverting input) controls the output amplitude; another resistor from pin 15 to the negative supply (pin 16) sets the dc output level. a 1:1 resistor ratio sets the output dc level at two v be with respect to v ee . a small capacitor from pin 17 to 15 can be used to set the bandwidth. 16 v ee2 o u t v ee2 16 det gain supply ground (v ee2 ) in the pcb layout, the ground pins (also applies to pin 26) should be connected directly to chassis ground. decoupling capacitors to v cc should be placed directly at the ground pins.
mc13158 9 motorola analog ic device data pin function description (continued) description/external circuit requirements internal equivalent circuit symbol pin 19 ds aoffo ds out 21 v cc2 7 data slicer off the data output may be shut off to save cur- rent by placing ds aoffo (pin 19) at v cc . 21 ds out ds gnd 22 cc2 data slicer output in the application example a 10 k w pullup resistor is connected to the collector of the output transistor at pin 21. 22 ds gnd ds aoffo 19 16 v ee2 64 k data slicer ground all the inverting switching stages in the comparator are supplied through the emitter pin of the output transistor (pin 22) to ground rather than internally to v ee in order to reduce switching feedback to the front end. 18 20 ds in1 ds in2 20 ds in2 16 v ee2 18 ds in1 v cc2 7 data slicer inputs the data slicer has differential inputs with back to back diodes across them. the recovered signal is dc coupled to ds in1 (pin 18) at nominally v 18 with respect to v ee ; thus, it will maintain v 18 v be at pin 18. ds in2 (pin 20) is ac coupled to v ee . the choice of coupling capacitor is dependent on the nature of the data signal. for small signal or continuous bits of the same polarity, the response time is relatively large. on the other hand, for large peak to peak voltage swings or when the dc level at the detector output changes, the response time is short. see the discussion in the application section for external circuit design details. 23 24 rssi buf rssi rssi buf 23 v ee2 16 24 rssi v cc2 7 2 v cc1 rssi buffer a unity gain amplifier is used to buffer the voltage at pin 24 to 23.the output of the unity gain buffer (pin 23) has an active pull up but no pull down. an external resistor is placed from pin 23 to v ee to provide the pull down. rssi the rssi output current creates a voltage drop across an external resistor from pin 24 to v ee . the maximum rssi current is 26 m a; thus, the maximum rssi voltage using a 100 k w resistor is approximately 2.6 vdc. fig- ure 22 shows the rssi output voltage versus input signal level in the application circuit. the negative slew rate is determined by an external capacitor and resistor to v ee (negative supply). the rssi rise and fall times for various rf input signal levels and r 24 values without the capacitor, c 24 are displayed in figure 24. this is the maximum response time of the rssi.
mc13158 10 motorola analog ic device data pin function description (continued) description/external circuit requirements internal equivalent circuit symbol pin 25 enable 2 v cc1 enable the ic regulators are enabled by placing this pin at v ee . 26 v ee1 v ee1 26 25 enable v cc2 7 v ee2 16 v ee1 26 v cc1 2 v cc and v ee esd protection esd protection diodes exist between the v cc and v ee pins. it is important to note that significant differences in potential (> 0.5 v be ) between the two v cc pins or between the v ee pins can cause these structures to start to conduct, thus compromising isolation between the supply busses. v cc1 & v cc2 should be maintained at the same dc potential, as should v ee1 & v ee2 . 28 29 osc base osc emitter osc base 28 v cc1 2 oscillator base this pin is connected to the base lead of the common collector transistor. since there is no internal bias resistor to the base, v cc is applied through an external choke or coil. oscillator emitter this pin is connected to the emitter lead; the ii di ll v ee1 26 osc emitter 29 p emitter is connected internally to a current source of about 200 m a. additional emitter current may be obtained by connecting an external resistor to v ee ; i e = v 29 /r 29 . details of circuits using overtone crystal and lc varactor controlled oscillators are discussed in the application section. 31 32 mix in1 mix in2 rf in2 32 26 v ee1 rf in1 31 2 v cc1 mixer inputs the parallel equivalent differential input impedance of the mixer is approximately 2.0 k w in parallel with 1.0 pf. this equates to a single ended input impedance of 1.0 k w in parallel with 2.0 pf. the application circuit utilizes a saw filter having a differential output that requires a 2.0 k w ii 2.0 pf load. therefore, little matching is required between the saw filter and the mixer inputs. this and alternative circuits are discussed in more detail in the application section.
mc13158 11 motorola analog ic device data applications information evaluation pc board the evaluation pcb is very versatile and is intended to be used across the entire useful frequency range of this device. the center section of the board provides an area for attaching all smt components to the circuit side and radial leaded components to the component ground side (see figures 29 and 30). additionally, the peripheral area surrounding the rf core provides pads to add supporting and interface circuitry as a particular application dictates. this evaluation board will be discussed and referenced in this section. component selection the evaluation pc board is designed to accommodate specific components, while also being versatile enough to use components from various manufacturers and coil types. figures 13 and 14 show the placement for the components specified in the application circuit (figure 12). the application circuit schematic specifies particular components that were used to achieve the results shown in the typical curves and tables but alternate components should give similar results.
mc13158 12 motorola analog ic device data figure 12. application circuit notes: 1. saw filter siemens part number y6970m(5 pin sip plastic package). 2. an lcr filter reduces the broadband noise in the if; ceramic filters may be used for data rates under 500 khz. 4.0 db insertion loss filters optimize the linearity of rssi. 3. the quadrature tank components are chosen to optimize linearity of the recovered signal while maintaining adequate recovered signal level. 1.5 m h 7.0 mm variable shielded inductor: toko part # 292snst1373z. the shunt resistor is approximately equal to q(2 p fl), where q ~ 18 (3.0 db bw = 600 khz). 4. the local oscillator circuit utilizes a 122.7 mhz, 5th overtone, series resonant crystal specified with a frequency tolerance of 25 ppm, esr of 120 w max. the oscillator configuration is an emitter coupled butler. 5. the 95 nh (nominal) inductor is a 7.0 mm variable shielded inductor: coilcraft part # 15004j08s or equivalent. 6. 0.68 m h axial lead chokes (molded inductor ): coilcraft part # 9011. 7. to enable the ic, pin 25 is taken to v ee . the external pull down resistor at pin 29 could be linked to the enable function; otherwise if it is taken to v ee as shown, it will keep the oscillator biased at about 500 m a depending on the v cc level. 8. the other resistors and capacitors are surface mount components. 100 n 25 32 31 30 29 28 27 26 24 23 22 21 20 19 18 17 enable v ee1 n/c n/c if amp lim amp 5.0 p bias mc13158 16 v ee2 15 14 n/c 12 11 n/c 10 9 2 3 4 5 6 7 8 v cc1 v cc2 1 100 n 100 n 1.0 n 1.0 n 100 n 100 n 100 n 680 p 150 100 p 39 p 1.0 n 1.0 n 1.5 m h 13 2.2 k 82 k ds out 4.7 k rf input (1) (4) 122.7 mhz 5th ot crystal saw filter sma v cc = 2.0 to 5.0 vdc 1.0 k 100 n 330 nh (2) lcr filter 330 nh 680 p (2) r 17 82 k 1.0 m c 17 quad detector c 20 ds in2 ds aoffo 10 k 1.0 n 100 k ds in1 10 n rssi out (7) enable 33 10 n (5) 95 nh 33 p (6) 0.68 m h 27 p mixer r 15 (3) lcr quad tank 150 112 mhz
mc13158 13 motorola analog ic device data figure 13. circuit side component placement mc13158 v cc mc13158fb 100n 1n 100p 1 m 100n 100n 100n 100n 1n 10n 100n 150 330nh 680p 39p 2.2k c17 82k c20 1.0k 100n 100n 150 330nh 10k 47k 1n 33p 27p 33 82k 1n 1n 100n 680p +
mc13158 14 motorola analog ic device data figure 14. ground side component placement v ee v cc ds off ds open/ in2 ds out rssi out rf input saw filter quad coil lo xtal 10.7 p ceramic filter 10.7 p ceramic filter 10.7 s ceramic filter 10.7 s ceramic filter mc13158 1.5 m h 95 ph 122.7 mhz 0.68 m h sma
mc13158 15 motorola analog ic device data input matching/components it is desirable to use a saw filter before the mixer to provide additional selectivity and adjacent channel rejection. in a wideband system the primary sensitivity of the receiver backend may be achieved before the last mixer. bandpass filtering in the limiting if is costly and difficult to achieve for bandwidths greater than 280 khz. the saw filter should be selected to easily interface with the mixer differential input impedance of approximately 2.0 k w in parallel with 1.0 pf. the pc board is dedicated to the siemens saw filter (part number y6970m); the part is designed for dect at 112 mhz 1st if frequency. it is designed for a load impedance of 2.0 k w in parallel with 2.0 pf; thus, no or little input matching is required between the saw filter and the mixer. the siemens saw filter has an insertion loss of typically 10 db and a 3.0 db bandwidth of 1.0 mhz. the relatively high insertion loss significantly contributes to the system noise and a filter having lower insertion loss would be desirable. in existing low loss saw filters, the required load impedance is 50 w ; thus, interface matching between the filter and the mixer will be required. figure 15 is a table of the singleended mixer input impedance. a careful noise analysis is necessary to determine the secondary contribution to system noise. figure 15. mixer input impedance (singleended) f (mhz) rs ( w ) xs ( w ) rp ( w ) xp ( w ) cp (pf) 50 930 350 1060 2820 1.1 100 480 430 865 966 1.6 150 270 400 860 580 1.8 200 170 320 770 410 1.9 250 130 270 690 330 1.85 300 110 250 680 300 1.8 400 71 190 580 220 1.8 500 63 140 370 170 1.9 600 49 110 300 130 2.0 system noise considerations the system block diagram in figure 16 shows the cascaded noise stages contributing to the system noise; it represents the application circuit in figure 12 and a low noise preamp using a mrf941 transistor (see figure 17). the preamp is designed for a conjugately matched input and output at 2.0 vdc v ce and 3.0 madc i c . sparameters at 2.0 v, 3.0 ma and 100 mhz are: s11 = 0.86, 20 s21 = 9.0, 164 s12 = 0.02, 79 s22 = 0.96, 12 the bias network sets v ce at 2.0 v and i c at 3.0 ma for v cc = 3.0 to 3.5 vdc. the preamp operates with 18 db gain and 2.7 db noise figure. in the cascaded noise analysis the system noise equation is: fsystem f1 [ ( f21 ) g1 ] [ ( f31 ) ] [ ( g1 )( g2 ) ] where: f1 = the noise factor of the preamp g1 = the gain of the preamp f2 = the noise factor of the saw filter g2 = the gain of the saw filter f3 = the noise factor of the mixer note: the proceeding terms are defined as linear relationships and are related to the log form for gain and noise figure by the following: f log 1 [(nf in db) 10] and similarly g log 1 [(gain in db) 10] the noise figure and gain measured in db are shown in the system block diagram. the mixer noise figure is typically 14 db and the saw filter adds typically 10 db insertion loss. addition of a low noise preamp having a 18 db gain and 2.7 db noise figure not only improves the system noise figure but it increases the reverse isolation from the local oscillator to the antenna input at the receiver. calculating in terms of gain and noise factor yields the following: f1 1.86; g1 63.1 f2 10; g2 0.1 f3 25.12 thus, substituting in the equation for system noise factor: fsystem 5.82; nfsystem 7.7 db
mc13158 16 motorola analog ic device data figure 16. system block diagram for noise analysis figure 17. 112 mhz lna noise source sawf lna mixer nf meter 150 p local oscillator f lo = 122.7 mhz g3 = 18 db nf3 = 14 db g1 = 18 db nf1 = 2.7 db f rf = 112 mhz g2 = 10 db nf2 = 10 db 47 330 nh 270 f if = 10.7 mhz 510 100 p 100 nh 1.0 k 8.2 k 15 k 100 n 3.5 vdc rf output 100 p fb 100 p 100 nh 1.0 k 680 nh 100 p mps3906 mrf941 rf input local oscillators vhf applications the onchip grounded collector transistor may be used for hf and vhf local oscillator with higher order overtone crystals. the local oscillator in the application circuit (figure 12) shows a 5th overtone oscillator at 122.7 mhz. this circuit uses a butler overtone oscillator configuration. the amplifier is an emitter follower. the crystal is driven from the emitter and is coupled to the high impedance base through a capacitive tap network. operation at the desired overtone frequency is ensured by the parallel resonant circuit formed by the variable inductor and the tap capacitors and parasitic capacitances of the onchip transistor and pc board. the variable inductor specified in the schematic could be replaced with a high tolerance, high q ceramic or air wound surface mount component if the other components have tight enough tolerances. a variable inductor provides an adjustment for gain and frequency of the resonant tank ensuring lock up and startup of the crystal oscillator. the overtone crystal is chosen with esr of typically 80 w and 120 w maximum; if the resistive loss in the crystal is too high the performance of oscillator may be impacted by lower gain margins. a series lc network to ground (which is v cc ) is comprised of the inductance of the base lead of the onchip transistor and pc board traces and tap capacitors. parasitic oscillations often occur in the 200 to 800 mhz range. a small resistor is placed in series with the base (pin 28) to cancel the negative resistance associated with this undesired mode of oscillation. since the base input impedance is so large a small resistor in the range of 27 to 68 w has very little effect on the desired butler mode of oscillation. the crystal parallel capacitance, c o , provides a feedback path that is low enough in reactance at frequencies of 5th overtones or higher to cause trouble. c o has little effect near resonance because of the low impedance of the crystal motional arm (r m l m c m ). as the tunable inductor which forms the resonant tank with the tap capacitors is tuned aoffo the crystal resonant frequency it may be difficult to tell if the oscillation is under crystal control. frequency jumps may occur as the inductor is tuned. in order to eliminate this behavior an inductor, l o , is placed in parallel with the crystal. l o is chosen to be resonant with the crystal parallel capacitance, c o, at the desired operation frequency. the inductor provides a feedback path at frequencies well below resonance; however, the parallel tank network of the tap capacitors and tunable inductor prevent oscillation at these frequencies. if filtering/matching in wideband data systems the if bandpass needed is greater than can be found in low cost ceramic filters operating at 10.7 mhz. it is necessary to bandpass limit with lc networks or seriesparallel ceramic filter networks. murata offers a seriesparallel resonator pair (part number
mc13158 17 motorola analog ic device data kmfc545) with a 3.0 db bandwidth of 325 khz and a maximum insertion loss of 5.0 db. the application pc board is laid out to accommodate this filter pair (a filter pair is used at both locations of the split if). however, even using a series parallel ceramic filter network yields only a maximum bandpass of 650 khz. in some applications a wider band if bandpass is necessary. a simple lc network yields a bandpass wider than the saw filter but it does reduce an appreciable amount of wideband if noise. in the application circuit an lc network is specified using surface mount components. the parallel lc components are placed from the outputs of the mixer and if amplifier to the v cc trace; internal 330 loads are connected from the mixer and if amplifier outputs to dec2 (pin 5 and 10 respectively).this loads the outputs with the optimal load impedance but creates a low insertion loss filter. an external shunt resistor may be used to widen the bandpass and to acquire the 10 db composite loss necessary to linearize the rssi output. the equivalent circuit is shown in figure 18. figure 18. if lcr filter 150 v cc r out 330 v cc 330 nh 680 p dec2 r in 330 5, 10 3, 8 2, 7 1, 6 dec1 4, 9 the following equations satisfy the 12 db loss (1:4 resistive ratio): (rext)(330) (rext 330) requivalent requivalent (requivalent 330) 1 4 solve for requivalent: 4(requivalent) requivalent 330 3(requivalent) 330 requivalent 110 substitute for requivalent and solve for rext: 330(rext) 110(rext) (330)(110) rext (330)(110) 220 rext 165 the if is 10.7 mhz although any if between 10 to 20 mhz could be used. the value of the coil is lowered from that used in the quadrature circuit because the unloaded q must be maintained in a surface mount component. a standard value component having an unloaded q = 100 at 10.7 mhz is 330 nh; therefore the capacitor is 669 pf. standard values have been chosen for these components; rext 150 c 680 pf l 330 nh computation of the loaded q of this lcr network is q requivalent x l where: x l = 2 p fl and requivalent is 103 w thus, q 4.65 the total system loss is 20 log (103 433) 12.5 db quadrature detector the quadrature detector is coupled to the if with an internal 5.0 pf capacitor between pins 12 and 13. for wideband data applications, the drive to the detector can be increased with an additional external capacitor between these pins; thus, the recovered signal level output is increased for a given bandwidth the wideband performance of the detector is controlled by the loaded q of the lc tank circuit. the following equation defines the components which set the detector circuit's bandwidth: q r t x l [1] where r t is the equivalent shunt resistance across the lc tank x l is the reactance of the quadrature inductor at the if frequency (x l = 2 p fl). the inductor and capacitor are chosen to form a resonant lc tank with the pcb and parasitic device capacitance at the desired if center frequency as predicted by f c [ 2 (lc p ) 1 2 ] 1 [2] where l is the parallel tank inductor c p is the equivalent parallel capacitance of the parallel resonant tank circuit. the following is a design example for a wideband detector at 10.7 mhz and a loaded q of 18. the loaded q of the quadrature detector is chosen somewhat less than the q of the if bandpass. for an if frequency of 10.7 mhz and an if bandpass of 600 khz, the if bandpass q is approximately 6.4. example: let the external cext = 139 pf. (the minimum value here should be much greater than the internal device and pcb parasitic capacitance, cint 3.0 pf). thus, c p = cint + cext = 142 pf. rewrite equation (2) and solve for l: l = (0.159) 2 /(c p fc 2 ) l = 1.56 m h; thus, a standard value is choosen: l = 1.56 m h (tunable shielded inductor) the value of the total damping resistor to obtain the required loaded q of 18 can be calculated by rearranging equation (1): r t q(2 fl) r t 18(2 )(10.7)(1.5) 1815
mc13158 18 motorola analog ic device data the internal resistance, rint at the quadrature tank pin 13 is approximately 13 k w and is considered in determining the external resistance, rext which is calculated from rext (( r t )( rint )) ( rint r t ) rext 2110; rext 2.2 k thus, choose the standard value: it is important to set the dc level of the detector output at pin 17 to center the peak to peak swing of the recovered signal. in the equivalent internal circuit shown in the pin function description, the reference voltage at the positive terminal of the inverting op amp buffer amplifier is set at 1.0 v be . the detector dc level, v 17 is determined by the following equation: v 17 [(( r 15 r 17 ) 1 ) ( r 15 r 17 ) ]v be thus, for a 1:1 ratio of r 15 /r 17 , v 17 = 2.0 v be = 1.4 vdc. similarly for a 2:1, v 17 = 1.5 v be = 1.05 vdc; and for 3:1, v 17 = 1.33 v be = 0.93 vdc. figure 19 shows the detector ascurveso, in which the resistor ratio is varied while maintaining a constant gain (r 17 is held at 62 k). r 15 is 62 k for a 1:1 ratio; while r 15 = 120 k and 180 k to produce the 2:1 and 3:1 ratios. the if signal into the detector is swept 500 khz about the 10.7 mhz if center frequency. the resulting curve show how the resistor ratio and the supply voltage effects the symmetry of the ascurveo (figure 21 test setup). for the 3:1 and 2:1 ratio, symmetry is maintained with v s from 2.0 to 5.0 vdc; however, for the 1:1 ratio, symmetry is lost at 2.0 vdc . figure 19. detector output voltage versus frequency deviation 600 2.5 detector output voltage, v (vdc) frequency deviation (khz) 2.0 1.5 1.0 0.5 0 400 200 0 200 400 600 r 15 :r 17 = 1:1 v s = 3.5 to 5.0 vdc r 15 :r 17 = 1:1 v s = 2.0 vdc r 15 :r 17 = 2:1 v s = 2.0 to 5.0 vdc r 15 :r 17 = 3:1 v s = 2.0 to 5.0 vdc 17 f c = 10.7 mhz r 17 = 62 k test setup figure 20 figure 20. demodulator ascurveo test setup wavetek signal generator model 134 oscilloscope tek 475 signal generator fluke 6082a f c = 10.7 mhz d f = 500 khz mc13158 50 w output sweep out x input y input ext mod in det out rf out lim in data slicer circuit c 20 at the input of the data slicer is chosen to maintain a time constant long enough to hold the charge on the capacitor for the longest strings of bits at the same polarity. for a data rate at 576 khz a bit stream of 15 bits at the same polarity would equate to an apparent data rate of approximately 77 kbps or 38 khz. the time constant would be approximately 26 m s. the following expression equates the time constant, t, to the external components: t 2 (r 18 )(c 20 ) solve for c 20 : c 20 t 2 (r 18 ) where the effective resistance r 18 is a complex function of the demodulator feedback resistance and the data slicer input circuit. in the data input network the back to back diodes form a charge and discharge path for the capacitor at pin 20; however, the diodes create a nonlinear response. this resistance is loaded by the ?, beta of the detector output transistor; beta =100 is a typical value (see figure 21). thus, the apparent value of the resistance at pin 18 (ds in1) is approximately equal to: r 18 r 17 100 where r 17 is 82 k w , the feedback resistor from pin 17 to 15. therefore, substituting for r 18 and solving for c 20 : c 20 15.9 (t) r 17 5.04 nf the closest standard value is 4.7 nf. figure 21. data slicer equivalent input circuit v cc r 18 r 17/ b 20 18 c 20
mc13158 19 motorola analog ic device data system performance data rssi in figure 22, the rssi versus rf input level shows the linear response of rssi over a 65 db range but it has extended capability over 80 db from 80 dbm to +10 dbm. the rssi is measured in the application circuit (figure 12) in which a saw filter is used before the mixer; thus, the overall sensitivity is compromised for the sake of selectivity. the curves are shown for three filters having different bandwidths: 1) lcr filter with 2.3 mhz 3.0 db bw (circuit and component placement is shown in figure 12) 2) seriesparallel ceramic filter with 650 khz 3.0 db bw (murata part # kmfc545) 3) ceramic filter with 280 khz 3.0 db bw. figure 22. rssi output voltage versus signal input level 90 3.0 rssi output voltage (vdc) signal input level (dbm) 2.7 2.4 2.1 1.8 1.5 1.2 0.9 80 70 60 50 40 30 20 20 10 10 0 0.6 0.3 0 seriesparallel ceramic filter ceramic filter lcr; rext = 150 w v cc = 4.0 vdc f rf = 112 mhz f lo = 122.7 mhz f if = 10.7 mhz see figure 12 for lcr filter ? ? ? ? ? ? ? ? ? ? ? ? ? ? ? ? ? ? ? ? ? ? ? ? ? ? ? ? ? ? ?? ?? ?? figure 23. rssi output rise and fall times versus rf input signal level 40 35 rssi rise and fall times, t & t ( s) rf input signal level (dbm) 30 25 20 15 10 5.0 0 0 20 60 80 rf m ?? ?? t r @ 47 k t r @ 22 k t f @ 22 k t f @ 47 k t f @ 100 k t r @ 100 k sinad performance figure 24 shows a test setup for a narrowband demodulator output response in which a cmessage filter and an active deemphasis filter is used following the demodulator. the input is matched using a 1:4 impedance transformer. the sinad performance is shown in figure 25 with no preamp and in figure 26 with a preamp (preamp figure 16). the 12 db sinad sensitivity is 101 dbm with no preamp and 113 dbm with the preamp. hp334 distortion analyzer hp8657b f c = 112 mhz f mod = 1.0 khz d f = 125 khz cmessage filter lo output input match lo in hp8657b f c = 122.7 mhz plo = 6.0 dbm mc13158 if 3.0 db bw = 280 khz active deemphasis rf voltmeter detector out n+d n figure 24. test setup for narrowband sinad
mc13158 20 motorola analog ic device data figure 25. s+n+d, n+d, n versus input signal level (without preamp) 120 10 s+n+d, n+d, n (db) rf input signal (dbm) 0 10 20 30 40 50 60 100 80 60 40 20 0 70 v s = 3.0 vdc f dev = 125 khz f mod = 1.0 khz f rf = 112 mhz if 3.0 db bw = 280 khz n+d n s+n+d figure 26. s+n+d, n+d, n versus input signal level (with preamp) 120 10 rf input signal (dbm) 0 10 20 30 40 50 60 100 80 60 40 20 0 figure 27. input ip3, 1.0 db compression pt. test setup 50 10 rf input signal level (dbm) 20 30 40 50 60 70 80 40 30 20 n +d n s+n+d 70 s+n+d, n+d, n (db) v s = 3.0 vdc f dev = 125 khz f mod = 1.0 khz f rf = 112 mhz if 3.0 db bw = 280 khz 60 1.0 db comp. pt. = 39 dbm ip3 = 32 dbm v s = 3.5 vdc f rf1 = 112 khz f rf2 = 112.1 khz f lo = 122.7 mhz plo = 6.0 dbm see figure 27 s+n+d, n+d, n (db) 50 50 112.1 mhz 112 mhz 100 p mixer 0.810 p 100 p 47 to spectrum analyzer fet probe tek p6201 f lo 122.7 mhz @ 6.0 dbm minicircuits zsfc4 4 way zero degree combiner local oscillator hp8657b g3 = 18 db nf3 = 14 db 270 figure 28. 1.0 db compression pt. and input third order intercept
mc13158 21 motorola analog ic device data figure 29. circuit side view mc13158 v cc 3.8
mc13158 22 motorola analog ic device data figure 30. ground side view v ee v cc ds off ds open/ in2 ds out rssi out rf input saw filter quad coil lo xtal 10.7 p ceramic filter 10.7 p ceramic filter 10.7 s ceramic filter 10.7 s ceramic filter mc13158
mc13158 23 motorola analog ic device data ftb suffix plastic package case 87301 (thin qfp) 0.274 0.274 0.055 0.010 0.051 0.010 0.005 0.013 6 0.005 5 0.006 0.348 0.006 5 0.348 min min max max millimeters inches dim 7.10 7.10 1.60 0.373 1.50 0.20 0.197 0.57 8 0.135 10 0.25 9.15 0.25 11 9.15 6.95 6.95 1.40 0.273 1.30 0.273 0.119 0.33 6 0.119 5 0.15 8.85 0.15 5 8.85 0.031 bsc 0.220 ref 0.016 bsc 0.80 bsc 5.6 ref 0.40 bsc a b c d e f g h j k l m n p q r s t u v x 0.280 0.280 0.063 0.015 0.059 0.008 0.008 0.022 8 0.005 10 0.010 0.360 0.010 11 0.360 notes: 1. dimensioning and tolerancing per ansi y14.5m, 1982. 2. controlling dimension: millimeter. 3. datum plane h is located at bottom of lead and is coincident with the lead where the lead exits the plastic body at the bottom of the parting line. 4. datums a, b and d to be determined at datum plane h. 5. dimensions s and v to be determined at seating plane c. 6. dimensions a and b do not include mold protrusion. allowable protrusion is 0.25 (0.010) per side. dimensions a and b do include mold mismatch and are determined at datum plane h. 7. dimension d does not include dambar protrusion. allowable dambar protrusion shall be 0.08 (0.003) total in excess of the d dimension at maximum material condition. dambar cannot be located on the lower radius or the foot. h datum plane x k detail c u t r q p detail a a,b,d b b j base metal d n section bb view rotated 90 clockwise f h datum plane h 32 25 24 17 16 9 8 1 v b b l a l d a s detail a c seating plane c e detail c m m g 1.0 ref 0.039 ref c 0.20 (0.008) ab d s s m 0.01 (0.004) h 0.20 (0.008) ab d s s m c 0.20 (0.008) ab d ab 0.05 (0.002) s s m 0.20 (0.008) c ab d 0.05 (0.002) ab m s s 0.20 (0.008) h ab d m s s outline dimensions
mc13158 24 motorola analog ic device data notes motorola reserves the right to make changes without further notice to any products herein. motorola makes no warranty, representation or guarantee regarding the suitability of its products for any particular purpose, nor does motorola assume any liability arising out of the application or use of any product or circuit, and specifically disclaims any and all liability, including without limitation consequential or incidental damages. atypicalo parameters which may be provided in motorola data sheets and/or specifications can and do vary in different applications and actual performance may vary over time. all operating parameters, including atypicalso must be validated for each customer application by customer's technical experts. motorola does not convey any license under its patent rights nor the rights of others. motorola products are not designed, intended, or authorized for use as components in systems intended for surgical implant into the body, or other applications intended to support or sustain life, or for any other application in which the failure of the motorola product could create a situation where personal injury or death may occur. should buyer purchase or use motorola products for any such unintended or unauthorized application, buyer shall indemnify and hold motorola and its officers, employees, subsidiaries, affiliates, and distributors harmless against all claims, costs, damages, and expenses, and reasonable attorney fees arising out of, directly or indirectly, any claim of personal injury or death associated with such unintended or unauthorized use, even if such claim alleges that motorola was negligent regarding the design or manufacture of the part. motorola and are registered trademarks of motorola, inc. motorola, inc. is an equal opportunity/affirmative action employer. how to reach us: usa / europe / locations not listed : motorola literature distribution; japan : nippon motorola ltd.; tatsumispdjldc, 6f seibubutsuryucenter, p.o. box 20912; phoenix, arizona 85036. 18004412447 or 6023035454 3142 tatsumi kotoku, tokyo 135, japan. 038135218315 mfax : rmfax0@email.sps.mot.com touchtone 6 022446609 asia / pacific : motorola semiconductors h.k. ltd.; 8b tai ping industrial park, internet : http://designnet.com 51 ting kok r oad, tai po, n.t., hong kong. 85226629298 mc13158/d ?

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